Direct digital access arrangement circuitry and method for connecting DSL circuitry to phone lines

ABSTRACT

An isolation system for terminating a phone line is provided. The invention may comprise a capacitive isolation barrier across which a digital signal is communicated. Clock recovery circuitry may be employed on one side of the isolation barrier to extract timing information from the digital signal communicated across the barrier. An isolated power supply may also be provided on the isolated side of the barrier, whereby direct current is generated in response to the digital data received across the isolation barrier. A bidirectional isolation system is provided whereby bidirectional communication of digital signals is accomplished using a single pair of isolation capacitors. In preferred embodiments, the digital data communicated across the barrier consists of digital delta-sigma data signals multiplexed in time with other digital control, signaling and framing information. Finally, the isolation system may include a pulse transformer to accommodate ADSL circuitry, whereby power is transmitted through the pulse transformer.

This is a continuation-in-part of U.S. Ser. No. 09/035,175 filed on Mar.4, 1998 now U.S. Pat. No. 6,385,235 which is a continuation-in-part ofU.S. Ser. Nos. 08/841,409 now U.S. Pat. No. 6,137,827, 08/837,702 nowU.S. Pat. No. 5,870,046 and 08/837,714 now U.S. Pat. No. 6,430,229 allfiled on Apr. 22, 1997. Further, the following U.S. patent applicationsfiled Mar. 4, 1998, Ser. No. 09/034,687, entitled “Digital IsolationSystem With Data Scrambling” by George Tyson Tuttle et al; Ser. No.09/034,456, entitled “Digital Isolation With ADC Offset Calibration; byAndrew W. Krone et al.; Ser. No. 09/034,455, entitled “Ring-DetectInterface Circuitry and Method for a Communication System” by Timothy J.Dupuis et al.; Ser. No. 09/035,779, entitled “Call Progress MonitorCircuitry and Method for a Communication System” by Timothy J. Dupuis etal.; Ser. No. 09/034,683, entitled “External Resistor and Method toMinimize Power Dissipation in DC Holding Circuitry for a CommunicationSystem” by Jeffrey W. Scott et al.; Ser. No. 09/034,620, entitled“Caller ID Circuit Powered Through Hook-switch Devices” by Jeffrey W.Scott et al.; and Ser. No. 09/034,682, entitled “Framed Delta Sigma DataWith Unlikely Delta Sigma Data Patterns” by Andrew W. Krone et al., areexpressly incorporated herein by reference.

TECHNICAL FIELD OF THE INVENTION

This invention relates to the field of isolation systems for use inselectively isolating electrical circuits from one another. Moreparticularly, this invention relates to isolation systems havingcapacitor-coupled isolation barriers and to direct digital accessarrangement circuitry for connecting to phone lines.

BACKGROUND

Electrical isolation barriers can be identified in many industrial,medical and communication applications where it is necessary toelectrically isolate one section of electronic circuitry from anotherelectronic section. In this context isolation exists between twosections of electronic circuitry if a large magnitude voltage source,typically on the order of one thousand volts or more, connected betweenany two circuit nodes separated by the barrier causes less than aminimal amount of current flow, typically on the order of tenmilliamperes or less, through the voltage source. An electricalisolation barrier must exist, for example, in communication circuitrywhich connects directly to the standard two-wire public switchedtelephone network and that is powered through a standard residentialwall outlet. Specifically, in order to achieve regulatory compliancewith Federal Communications Commission Part 68, which governs electricalconnections to the telephone network in order to prevent network harm,an isolation barrier capable of withstanding 1000 volts rms at 60 Hzwith no more than 10 milliamps current flow, must exist betweencircuitry directly connected to the two wire telephone network andcircuitry directly connected to the residential wall outlet.

In many applications there exists an analog or continuous time varyingsignal on one side of the isolation barrier, and the informationcontained in that signal must be communicated across the isolationbarrier. For example, common telephone network modulator/demodulator, ormodem, circuitry powered by a residential wall outlet must typicallytransfer an analog signal with bandwidth of approximately 4 kilohertzacross an isolation barrier for transmission over the two-wire, publicswitched telephone network. The isolation method and associatedcircuitry must provide this communication reliably and inexpensively. Inthis context, the transfer of information across the isolation barrieris considered reliable only if all of the following conditions apply:the isolating elements themselves do not significantly distort thesignal information, the communication is substantially insensitive to orundisturbed by voltage signals and impedances that exist between theisolated circuitry sections and, finally, the communication issubstantially insensitive to or undisturbed by noise sources in physicalproximity to the isolating elements.

High voltage isolation barriers are commonly implemented by usingmagnetic fields, electric fields, or light. The corresponding signalcommunication elements are transformers, capacitors and opto-isolators.Transformers can provide high voltage isolation between primary andsecondary windings, and also provide a high degree of rejection of lowervoltage signals that exist across the barrier, since these signalsappear as common mode in transformer isolated circuit applications. Forthese reasons, transformers have been commonly used to interface modemcircuitry to the standard, two-wire telephone network. In modemcircuitry, the signal transferred across the barrier is typically analogin nature, and signal communication across the barrier is supported inboth directions by a single transformer. However, analog signalcommunication through a transformer is subject to low frequencybandwidth limitations, as well as distortion caused by corenonlinearities. Further disadvantages of transformers are their size,weight and cost.

The distortion performance of transformer coupling can be improved whilereducing the size and weight concerns by using smaller pulsetransformers to transfer a digitally encoded version of the analoginformation signal across the isolation barrier, as disclosed in U.S.Pat. No. 5,369,666, “MODEM WITH DIGITAL ISOLATION” (incorporated hereinby reference). However, two separate pulse transformers are disclosedfor bidirectional communication with this technique, resulting in a costdisadvantage. Another disadvantage of transformer coupling is thatadditional isolation elements, such as relays and opto-isolators, aretypically required to transfer control signal information, such as phoneline hook-switch control and ring detect, across the isolation barrier,further increasing the cost and size of transformer-based isolationsolutions.

Because of their lower cost, high voltage capacitors have also beencommonly used for signal transfer in isolation system circuitry.Typically, the baseband or low frequency analog signal to becommunicated across the isolation barrier is modulated to a higherfrequency, where the capacitive isolation elements are more conductive.The receiving circuitry on the other side of the barrier demodulates thesignal to recover the lower bandwidth signal of interest. For example,U.S. Pat. No. 5,500,895, “TELEPHONE ISOLATION DEVICE” (incorporatedherein by reference) discloses a switching modulation scheme applieddirectly to the analog information signal for transmission across acapacitive isolation barrier. Similar switching circuitry on thereceiving end of the barrier demodulates the signal to recover theanalog information. The disadvantage of this technique is that theanalog communication, although differential, is not robust. Mismatchesin the differential components allow noise signals, which cancapacitively couple into the isolation barrier, to easily corrupt boththe amplitude and timing (or phase) of the analog modulated signal,resulting in unreliable communication across the barrier. Even withperfectly matched components, noise signals can couple preferentiallyinto one side of the differential communication channel. This schemealso requires separate isolation components for control signals, such ashookswitch control and ring detect, which increase the cost andcomplexity of the solution.

The amplitude corruption concern can be eliminated by other modulationschemes, such as U.S. Pat. No. 4,292,595, “CAPACITANCE COUPLED ISOLATIONAMPLIFIER AND METHOD,” which discloses a pulse width modulation scheme;U.S. Pat. No. 4,835,486 “ISOLATION AMPLIFIER WITH PRECISE TIMING OFSIGNALS COUPLED ACROSS ISOLATION BARRIER,” which discloses avoltage-to-frequency modulation scheme; and U.S. Pat. No. 4,843,339“ISOLATION AMPLIFIER INCLUDING PRECISION VOLTAGE-TO-DUTY CYCLE CONVERTERAND LOW RIPPLE, HIGH BANDWIDTH CHARGE BALANCE DEMODULATOR,” whichdiscloses a voltage-to-duty cycle modulation scheme. (All of theabove-referenced patents are incorporated herein by reference.) In thesemodulation schemes, the amplitude of the modulated signal carries noinformation and corruption of its value by noise does not interfere withaccurate reception. Instead, the signal information to be communicatedacross the isolation barrier is encoded into voltage transitions thatoccur at precise moments in time. Because of this required timingprecision, these modulation schemes remain analog in nature.Furthermore, since capacitively coupled noise can cause timing (orphase) errors of voltage transitions in addition to amplitude errors,these modulation schemes remain sensitive to noise interference at theisolation barrier.

Another method for communicating an analog information signal across anisolation barrier is described in the Silicon Systems, Inc. data sheetfor product number SSI73D2950. (See related U.S. Pat. Nos. 5,500,894 for“TELEPHONE LINE INTERFACE WITH AC AND DC TRANSCONDUCTANCE LOOPS” and5,602,912 for “TELEPHONE HYBRID CIRCUIT”, both of which are incorporatedherein by reference.) In this modem chipset, an analog signal withinformation to be communicated across an isolation barrier is convertedto a digital format, with the amplitude of the digital signal restrictedto standard digital logic levels. The digital signal is transmittedacross the barrier by means of two, separate high voltage isolationcapacitors. One capacitor is used to transfer the digital signal logiclevels, while a separate capacitor is used to transmit a clock or timingsynchronization signal across the barrier. The clock signal is used onthe receiving side of the barrier as a timebase for analog signalrecovery, and therefore requires a timing precision similar to thatrequired by the analog modulation schemes. Consequently one disadvantageof this approach is that noise capacitively coupled at the isolationbarrier can cause clock signal timing errors known as jitter, whichcorrupts the recovered analog signal and results in unreliablecommunication across the isolation barrier. Reliable signalcommunication is further compromised by the sensitivity of the singleended signal transfer to voltages that exist between the isolatedcircuit sections. Further disadvantages of the method described in thisdata sheet are the extra costs and board space associated with otherrequired isolating elements, including a separate high voltage isolationcapacitor for the clock signal, another separate isolation capacitor forbidirectional communication, and opto-isolators and relays forcommunicating control information across the isolation barrier.

Opto-isolators are also commonly used for transferring informationacross a high voltage isolation barrier. Signal information is typicallyquantized to two levels, corresponding to an “on” or “off” state for thelight emitting diode (LED) inside the opto-isolator. U.S. Pat. No.5,287,107 “OPTICAL ISOLATION AMPLIFIER WITH SIGMA-DELTA MODULATION”(incorporated herein by reference) discloses a delta-sigma modulationscheme for two-level quantization of a baseband or low frequency signal,and subsequent communication across an isolation barrier throughopto-isolators. Decoder and analog filtering circuits recover thebaseband signal on the receiving side of the isolation barrier. Asdescribed, the modulation scheme encodes the signal information intoon/off transitions of the LED at precise moments in time, therebybecoming susceptible to the same jitter (transition timing) sensitivityas the capacitive isolation amplifier modulation schemes.

Another example of signal transmission across an optical isolationbarrier is disclosed in U.S. Pat. No. 4,901,275 “ANALOG DATA ACQUISITIONAPPARATUS AND METHOD PROVIDED WITH ELECTRO-OPTICAL ISOLATION”(incorporated herein by reference). In this disclosure, ananalog-to-digital converter, or ADC, is used to convert several,multiplexed analog channels into digital format for transmission to adigital system. Opto-isolators are used to isolate the ADC fromelectrical noise generated in the digital system. Serial datatransmission across the isolation barrier is synchronized by a clocksignal that is passed through a separate opto-isolator. The ADC timebaseor clock, however, is either generated on the analog side of the barrieror triggered by a software event on the digital side of the barrier. Ineither case, no mechanism is provided for jitter insensitivecommunication of the ADC clock, which is required for reliable signalreconstruction, across the isolation barrier. Some further disadvantagesof optical isolation are that opto-isolators are typically moreexpensive than high voltage isolation capacitors, and they areunidirectional in nature, thereby requiring a plurality ofopto-isolators to implement bidirectional communication.

Thus, there exists an unmet need for a reliable, accurate andinexpensive apparatus for effecting bidirectional communication of bothanalog signal information and control information across a high voltageisolation barrier, while avoiding the shortcomings of the prior art.

SUMMARY OF THE INVENTION

The above-referenced deficiencies in the prior art are addressed by thepresent invention, which provides a reliable, inexpensive, lightweightisolation system that is substantially immune to noise that affects thetiming and/or amplitude of the signal that is transmitted across theisolating element, thus permitting an input signal to be accuratelyreproduced at the output of the isolation system.

The present invention provides digital direct access arrangement (DAA)circuitry that may be used to terminate the telephone connections at theuser's end that provides a communication path for signals to and fromthe phone lines. Briefly described, the invention provides a means fortransmitting and receiving a signal across a capacitive isolationbarrier. The signal is digitized and quantized to standard logic levelsfor transmission through the barrier, and is therefore largely immune toamplitude noise interference. In one embodiment of the invention, thedigital signal is synchronous and the signal is re-timed or latched onthe receiving side of the isolation barrier using a clock signal that isrecovered from the digital data sent across the barrier. The clockrecovery circuit provides a means for filtering jitter on the receiveddigital data so that the clock recovered has substantially less jitterthan the received digital signal. Consequently, the digitalcommunication across the capacitive isolation barrier is also largelyimmune to timing or phase noise interference. The DAA circuitry may beused to transmit and receive DSL information.

DESCRIPTION OF THE DRAWINGS

So that the manner in which the herein described advantages and featuresof the present invention, as well as others which will become apparent,are attained and can be understood in detail, more particulardescription of the invention summarized above may be had by reference tothe embodiments thereof which are illustrated in the appended drawings,which drawings form a part of this specification.

It is noted, however, that the appended drawings illustrate onlyexemplary embodiments of the invention and are therefore not to beconsidered limiting of its scope, for the invention may admit to otherequally effective embodiments.

FIG. 1 is a block diagram of a telephone set illustrating a typicalapplication of the present invention.

FIG. 2 is a block diagram showing a unidirectional isolation systemaccording to the present invention.

FIG. 3A is a block diagram detailing the circuitry used to provide atwo-phase, non-overlapping clock signal to the delta-sigma modulatorsthat are used in preferred embodiments of this invention.

FIG. 3B is a timing diagram that illustrates timing relationshipsbetween various clock and data signals that occur in the circuitry ofthe present invention.

FIGS. 4A and 4B are diagrams that illustrate signal formats that may beproduced by the encoders used in this invention.

FIG. 5 is a block diagram showing the components of exemplary clockrecovery circuit that is used in the present invention.

FIGS. 6A and 6B are schematic diagrams of active diode bridge circuitsthat may be used as power supplies in preferred embodiments of thepresent invention.

FIG. 7 is a block diagram illustrating a bidirectional isolation systemaccording to the present invention.

FIG. 8 is a block diagram of a clock recovery and data synchronizationcircuit according to a preferred embodiment of the present invention.

FIG. 9 is a schematic diagram of a phase detector circuit that may beused in a clock recovery circuit according to a preferred embodiment ofthe present invention.

FIG. 10 is a schematic diagram of a frequency detector circuit that maybe used in a clock recovery circuit according to a preferred embodimentof the present invention.

FIG. 11 is a block diagram of a decoder circuit that may be utilized ina preferred embodiment of the present invention.

FIG. 12 is an illustration representing a framing format that may bebeneficially used in preferred embodiments of the present invention.

FIGS. 13A and 13B are schematic diagrams of driver circuits that may beutilized to implement the present invention.

FIG. 14 is a timing diagram illustrating an alternative framing formatthat may be used in bidirectional embodiments of the present invention.

FIG. 15 is a block diagram of a clock recovery circuit that may beemployed for use with the framing format of FIG. 14.

FIG. 16 is a general block diagram of digital DAA circuitry includingphone line side circuitry, an isolation barrier, and powered sidecircuitry according to the present invention.

FIG. 17 is a general block diagram of transmit and receive signal pathswithin digital DAA circuitry according to the present invention.

FIG. 18 is a general circuit diagram of digital DAA circuitryimplemented with two integrated circuits (ICs) and a capacitiveisolation barrier according to the present invention.

FIG. 19 is a block diagram illustrating an application of the presentinvention in an ADSL environment.

FIG. 20 is illustrates a preferred embodiment of the present inventionshown in FIG. 19.

DESCRIPTION OF PREFERRED EMBODOMENTS

In order to provide a context for understanding this description, FIG. 1illustrates a typical application for the present invention: a telephonethat includes circuitry powered by a source external to the phonesystem. A basic telephone circuit 118 is powered by the “battery”voltage that is provided by the public telephone system and does nothave a separate power connection. Many modern phones 110, however,include radio (cordless), speakerphone, or answering machine featuresthat require an external source of power 112, typically obtained byplugging the phone (or a power supply transformer/rectifier) into atypical 110-volt residential wall outlet. In order to protect publicphone system 114 (and to comply with governmental regulations), it isnecessary to isolate “powered circuitry” 116 that is externally poweredfrom “isolated circuitry” 118 that is connected to the phone lines, toprevent dangerous or destructive voltage or current levels from enteringthe phone system. (Similar considerations exist in many otherapplications as well, including communication, medical andinstrumentation applications in which this invention may be beneficiallyapplied.) The required isolation is provided by isolation barrier 120.The signal that passes through the isolation barrier 120 is an analogvoice signal in a typical telephone application, but it may also be adigital signal or a multiplexed signal with both analog and digitalcomponents in various applications. In some applications, communicationacross isolation barrier 120 may be unidirectional (in eitherdirection), but in many applications, including telephony, bidirectionalcommunication is required. Bidirectional communication may be providedusing a pair of unidirectional isolator channels, or by forming a singleisolation channel and multiplexing bidirectional signals through thechannel.

The primary requirements placed on isolation barrier 120 are that iteffectively prevents harmful levels of electrical power from passingacross it, while accurately passing the desired signal from the poweredside 122 to the isolated side 124, or in the reverse direction ifdesired.

FIG. 2 illustrates a basic block diagram of a preferred embodiment ofthe present invention. First the overall operation of the invention willbe described, and then each component will be described in detail to theextent required to enable a person skilled in the art to make and usethe invention. As a matter of terminology, the circuitry shown on theleft or powered side of the isolation barrier (capacitors 209 and 210 inFIG. 2) will be referred to as the “powered” circuitry or the “transmit”circuitry or system, and the circuitry on the right side of theisolation barrier will be referred to as the “isolated” or “receive”circuitry or system. The “transmit” side can ordinarily be identified bythe location of the dominant master oscillator 202 on that side of thebarrier, and the slave oscillator (e.g. clock recovery circuit 216) islocated on the receive side. Note, however, that in some embodiments ofthe present invention signals may be transmitted from the receive systemto the transmit system, so these terms do not necessarily indicate thedirection of data flow across the barrier. Furthermore, in someembodiments the master oscillator may be on the low-power (e.g.telephone system) side of the barrier, and a clock recovery PLL may belocated on the high-power side of the barrier.

Referring to FIG. 2, a preferred unidirectional capacitive isolationsystem according to the present invention includes a delta-sigma analogto digital converter 201 operable on the analog input 212 and driven bya clock signal from oscillator 202. The digital output of thedelta-sigma ADC 224 is synchronous with the operating frequency ofoscillator 202 and time division multiplexed with digital controlsignals 219 by encoder circuit 213. The encoder circuit 213 also formatsthe resulting digital data stream 230 into a coding scheme or framingformat that allows for robust clock recovery on the receiving side ofthe isolation barrier. The isolation barrier comprises two high voltagecapacitors 209 and 210. In one embodiment of the present invention,driver circuit 214 drives the transmit side of capacitor 209 with adigital voltage signal. Clock recovery circuit 216 presents a very highimpedance to the receive side of capacitor 209, allowing the digitalvoltage output of driver 214 to couple across the isolation barrier. Inthis embodiment, capacitor 210 provides a return current path across thebarrier. In another embodiment, capacitors 209, 210 are differentiallydriven by complementary digital outputs of driver circuit 214. In thatembodiment, clock recovery circuit 216 presents a very high impedance tothe receive sides of capacitors 209 and 210, allowing the differentialdigital voltage outputs of driver 214 to couple across the isolationbarrier. The input to driver circuit 214 is the output 230 of encoder213.

The receive side of the isolation barrier includes clock recoverycircuit 216, with inputs connected to isolation capacitors 209 and 210.The clock recovery circuit recovers a clock signal from the digital datadriven across the isolation barrier. The recovered clock providesclocking signals for decoder 217 and delta-sigma digital-to-analogconverter 208. Decoder circuit 217 separates the time divisionmultiplexed data signal from control signals, providing a digitalcontrol output 228 and data output 232 that is routed to delta-sigma DAC208. The delta-sigma DAC 208, with digital input supplied from decoder217 and clock supplied from clock recovery circuit 216, provides theanalog output of the receive side of the isolation system, which closelycorresponds to the original analog input 212.

Active diode bridge circuit 640 may also be connected to isolationcapacitors 209 and 210 to provide a DC voltage source 220 to clockrecovery circuit 216 and decoder circuit 217 derived from energycontained in the signal transmitted across the isolation barrier.

In the descriptions of preferred embodiments that follow, all circuitreferences are made with respect to MOS (metal oxide-semiconductor)integrated circuit technology, although the invention may be implementedin other technologies as well, as will be understood by one skilled inthe art. A preferred embodiment incorporates transmit system 225consisting of delta-sigma ADC 201, oscillator 202, encoder 213 anddriver 214 fabricated on one silicon substrate, and receive system 226consisting of clock recovery circuit 216, decoder 217, delta-sigma DAC208 and active diode bridge 640 fabricated on a second siliconsubstrate. The two separate silicon substrates are required to maintainthe high voltage isolation provided by capacitors 209 and 210, sincetypical MOS technologies cannot provide high voltage isolation of 1000volts or greater.

The delta-sigma analog-to-digital converter, shown as block 201 of FIG.2, is well known in the art. See, for example, J. C. Candy, A Use ofDouble Integration in Sigma Delta Modulation, IEEE Trans. OnCommunication, March 1985, pp. 249-258, and B. E. Boser and B. A.Wooley, The Design of Sigma-Delta Modulation Analog-to-DigitalConverters, IEEE Journal Solid State Circuits, December 1988, pp.1298-1308, both of which are incorporated herein by reference. Thespecific design of ADC 201 will be a matter of design choice dependingupon the needs of the particular application in which the isolationbarrier will be used.

The use of a delta-sigma converter within the isolation system providesseveral desirable features. It will be appreciated that the delta-sigmaconverter uses a high oversampling rate to provide accurate A/Dconversion over the input signal bandwidth without the use of preciselymatched components or high-order, analog anti-aliasing filters.Moreover, such converters occupy a relatively small amount of space onan integrated circuit and are relatively easy to fabricate on a CMOSchip.

The digital pulse stream 224 output from delta-sigma converter 201encodes the analog input signal 212 in a pulse density modulationformat. In pulse density modulation, the amplitude information of theanalog input signal is contained in the density of output pulsesgenerated during a given interval of time.

Suitable designs for oscillator circuit 202 are well known in the artand may typically comprise a ring oscillator, relaxation oscillator, oran oscillator based on a piezo-electric crystal disposed external to theintegrated MOS circuit. See, for example, A. B. Grebene, Bipolar and MOSAnalog Integrated Circuit Design, John Wiley and Sons, 1984, which isincorporated herein by reference. FIG. 3A further illustrates the clocksignals that may be provided to delta-sigma converter 201 in a preferredembodiment of this invention. Clock signal 302 from oscillator 202 isinput to clock divider circuit 304 that divides the frequency of theinput clock and provides an output in the form of two phase,non-overlapping clock signals ₁ and ₂ to the delta-sigma modulatorcircuit. The design and construction of clock divider circuit 304 iswithin the ordinary skill in the art and is not detailed here. Sinceencoder circuit 213 may perform time-division multiplexing of thedigitized data signal 224 with digital control input data 219 using atime base derived from oscillator 202, clock divider 304 of FIG. 3A musttypically divide the frequency of oscillator 202 by at least a factor oftwo.

FIG. 3B illustrates exemplary signals associated with clock dividercircuit 304 and delta-sigma modulator 201 in FIG. 3A. Trace 310 is theclock signal received from oscillator 202 on line 302. Trace 312 is the“clock divided by 2” signal that is generated by clock divider circuit304. Traces 314 and 316 illustrate exemplary two phase, non-overlappingclock signals ₁ and ₂, respectively, that may be output from clockdivider circuit 304 to delta-sigma modulator 201. Trace 318 representsthe analog input to ADC 201, which generally changes very slowly incomparison to the frequency of clock signal 310. This bandwidthrelationship is required because the delta-sigma modulator must operateat a sampling rate much higher than a typical Nyquist rate (for example,a 1 MHz sampling rate for a 4 kHz voiceband signal is typical) in orderfor the information in the analog signal to be accurately represented bythe single-bit binary output. Finally, trace 320 represents the digitaloutput of delta-sigma modulator 201, which may, for example, besynchronized to the rising edge of clock signal ₁. (The illustratedoutput bit pattern 320 is provided to show exemplary timingrelationships and does not attempt to accurately reflect the illustratedanalog input 318).

Referring to FIG. 2, the encoder circuit 213 performs two primaryfunctions in preferred embodiments of this invention. The first functionof encoder 213 is time-division multiplexing of control signals 219 fromother circuitry and data signals 224 from the delta-sigma modulator 201,an operation that is well known in the art and subject to many suitableimplementations. The multiplexing function is synchronized by clocksignals from oscillator 202. The second function of encoder 213 isformatting the data for transmission across isolation capacitors 209,210. FIG. 4 details one coding scheme that may be used to transmitdigital pulses across the capacitive isolation barrier. (Anothersuitable coding scheme is described below with reference to FIG. 14.)FIG. 4A shows the format for data sent from the transmit circuit to thereceive circuit. When data=1 for a given bit cell, the output of theencoder is high for the first quarter of the bit cell period. Whendata=0 for a given bit cell, the output of the encoder is high for thethird quarter of the bit cell period. This coding scheme guarantees onelow-to-high transition followed by one high-to-low transition for everybit cell period, independent of the data pattern. The resulting dataindependent transition density allows for robust clock recovery in thereceiving circuitry on the other side of isolation capacitors 209, 210.Alternatively, robust clock recovery can also be achieved by use of apreamble used for frequency locking followed by a data pattern which isnot of constant average frequency.

In a bidirectional system, as is described below in connection with FIG.7, the transmit system encoder 702 and driver 703 may cooperate toprovide a high-impedance tri-state output to the isolation capacitor 705during either the last half of the bit cell period 410 (if transmitdata=1) or the first half of the bit cell period 411 (if transmitdata=0) as shown in FIG. 4A. This permits transmission of informationfrom the receive system to the transmit system during that portion ofeach bit cell when the transmit driver 703 is tri-stated.

In a preferred embodiment, at the beginning of each bit cell period thereceive system decoder section 708 detects whether the transmit circuithas sent a data=1 pulse across the isolation barrier. If a transmitdata=1 pulse was sent, the receive driver remains tri-stated until thesecond half of the bit cell period, during which time a receive data=0or 1 pulse can be sent back across the isolation barrier to the transmitsystem. If a transmit data=1 pulse is not detected by the receivecircuit the receive driver sends receive data=0 or 1 during the firsthalf of the bit cell period and tri-states for the second half of thebit cell period. This operation is shown in FIG. 4B.

In those embodiments in which the digital, bidirectional communicationis differential, capacitors 705 and 706 are driven by complementarydigital voltages in both directions, and the driver circuits associatedwith both capacitors are tri-stated during selected portions of the bitcell period in accordance with the coding scheme shown in FIG. 4.

A preferred embodiment of the unidirectional driver circuit 214 of FIG.2 is detailed in FIG. 13A for single ended (not differential)communication and FIG. 13B for differential communication across thecapacitive isolation barrier. Referring to FIG. 13A, the transmitcircuit driver 214 may comprise an inverter 250 driven by the encoderoutput signal 230. The output of inverter 250 drives the transmitcircuit side of isolation capacitor 209 to transmit logic levels definedby the transmit VDD and ground voltage levels. The clock recovery inputbuffer presents a high impedance to the receive side of capacitor 209,thereby allowing the receive side of capacitor 209 to attainsubstantially the same logic levels as the transmit side of capacitor209. In this manner the digital logic signal is effectively coupledacross the capacitive isolation barrier.

Capacitor 210 is disposed between the transmit circuit ground node 254and receive circuit ground node 256 in order to form a ground currentreturn path across the isolation barrier. This path is required becausethe clock recovery buffer input impedance, although high, is notinfinite. Therefore a small current must flow across the barrier andback in order to couple the digital logic signal across the barrier.Furthermore, capacitor 209 must deliver charge to the active diodecircuit 640 (FIG. 2) in order that a supply voltage for several receivecircuit sections can be provided. The current associated with thistransfer of charge from the transmit circuit to the receive circuit musthave a path to return to the transmit circuit.

The single-ended communication system described above is insensitive tovoltage signals that may exist between the transmit circuit ground 254and receive circuit ground 256 provided that the rate of change of suchvoltage signals is substantially less than the frequency of the digitalsignal transmitted across the barrier. The single-ended method is alsoinsensitive to resistive and capacitive impedances that may existbetween the transmit circuit ground 254 and receive circuit ground 256.The system can be desensitized to inductive impedances that may existbetween the transmit circuit ground 254 and receive circuit ground 256by adding resistive elements in series with capacitor 210, in serieswith the transmit ground connection 254, in series with the receiveground connection 256, or any combination of these.

FIG. 13B shows an example of a suitable differential driver 258 forunidirectional digital communication across a capacitive isolationbarrier. The inverter 260 that drives capacitor 209 is driven by thedigital signal output from the transmit encoder circuit 213, whileinverter 261, which drives capacitor 210, is driven by the complement231 of the digital signal output from transmit encoder circuit 213.Clock recovery input buffer 262 presents high impedances to the receivesides of capacitors 209 and 210, allowing the differential digitaltransmit voltages to couple across the isolation barrier. In thisdifferential communication method, both capacitors 209 and 210 providereturn current paths across the isolation barrier. The differentialdigital communication system described above is largely insensitive tovoltage signals and impedances that may exist between the transmitcircuit ground 254 and receive circuit ground 256 , since these voltagesand impedances appear as common mode influences in differentialcommunication.

Bidirectional communication across the barrier can be supported byadditional driver and receive buffer structures, similar to those shownin FIG. 13, without the need for any additional isolation elements,providing that inverters 250, 260, 261, which drive the high voltageisolation capacitors, can be tri-stated generally in accordance with thetiming diagram shown in FIG. 4 or any other suitable coding and timingscheme. In some embodiments, additional capacitor driving inverters thatcan be tri-stated may be provided in a receive-side driver circuit 713(FIG. 7) and input buffers may be provided in a transmit side decodercircuit 714.

In presently preferred embodiments, the actual isolation barriercomprises a pair of isolation capacitors 209 and 210, which are highvoltage capacitors that may be chosen for a particular application toprevent DC and low frequency current flow across the barrier and protectthe isolated circuitry from high voltage faults and transients, whilepermitting data at selected transmission frequencies to cross thebarrier. The capacitors must be capable of withstanding anticipatedvoltages that may appear due to faults in the powered circuitry 225, inorder to provide the protective function that is the purpose of thebarrier. For example, in preferred embodiments ordinary 2000 voltcapacitors with capacitance on the order of 100 pF may be utilized inthe isolation barrier. In a barrier system in accordance with thepresent invention it is not necessary to use high precision capacitors,because the system is very tolerant of variations in capacitorperformance due to environmental influences, such as variations involtage and temperature.

A preferred embodiment for a clock recovery circuit 216 for use in thisinvention is detailed in FIG. 5 and described below. One section of theclock recovery circuit may be a phase locked loop (“PLL”) circuit,consisting of phase/frequency detector 531, charge pump 532, resistor533, capacitor 534, and voltage controlled oscillator (“VCO”) 535. Theother section of the clock recovery block is data latch 542 operatingoutside the phase locked loop to re-time the digital data receivedacross the isolation barrier. Circuitry for performing these functionsis well known to those skilled in the art. See, for example, F. Gardner,Phaselock Techniques, 2d ed., John Wiley & Sons, NY, 1979; and R. Best,Phase-Locked Loops, McGraw-Hill, 1984, which are incorporated herein byreference. The data input to the receive system from the isolationcapacitors may be derived from a differential signal present at thebarrier by passing the differential signal through MOS input buffers(not shown), which are well known in the art, and providing asingle-ended binary output signal 530 to the clock recovery circuit.

The illustrated exemplary phase/frequency detector 531 receives adigital input 530 from the isolation barrier and an input 536 from theoutput of VCO 535 and performs a phase comparison between these twoinputs. If the VCO phase lags the input data phase, a speed up signal538 is supplied to charge pump 532. If the input data 530 phase lags theVCO output 536 phase, a slow down signal 540 is supplied to charge pump532. In response to “speed up” inputs from phase/frequency detector 531,charge pump 532 delivers a positive current to the loop filterconsisting of resistor 533 and capacitor 534 connected in series. Inresponse to “slow down” inputs from the phase/frequency detector, chargepump 532 sinks a positive current from the loop filter. The outputvoltage of the loop filter at node 542 drives voltage controlledoscillator 535, which increases its operation frequency as the inputvoltage increases. The output of VCO 535 is fed back as input 536 tophase/frequency detector 531, and it is also used to re-time the inputdata 530 by serving as the clock input to flip-flop latch 542, thusproviding a clock signal to the isolated circuitry and also providingdata signal 546 that is synchronized to clock signal 544. A dividercircuit may be included in the feedback path 536.

The phase/frequency detector and charge pump operate to increase loopfilter voltage 542 and VCO frequency if VCO phase 536 lags input dataphase 530. Conversely, the VCO frequency is decreased if the VCO phaseleads input data phase. In this manner, the VCO output phase is adjusteduntil phase lock is achieved with input data. Consequently, the VCOfrequency is driven to be substantially identical to the input datafrequency.

If noise interference occurs at the isolation barrier, the input datatransitions will occur at points in time that are noisy, or jittered,relative to the transition times of the transmit circuit driver. Thesejittered data edges will cause a noise component in the charge pumpcurrent that drives the loop filter. The loop filter and VCO, however,low-pass filter this noise component, substantially attenuating theeffects of this input data jitter. Consequently, the VCO output signal,while frequency locked to the input data, contains substantially lessphase noise than the noisy input data. The bandwidth of the phase noisefiltering operation may be set independently of the bandwidth of theanalog signal to be communicated across the isolation barrier. Since thefiltered, phase locked loop output clock signal 544 is used to latch orre-time the noisy input data at flip flop 542, the effects of noiseinterference at the capacitive isolation barrier are substantiallyeliminated. Finally, the filtered, phase locked loop output clock signal544 is used as the timebase or clock for the other receive circuits,including decoder 217 and delta-sigma DAC 208 shown in FIG. 2, resultingin an analog output 218 of the capacitive isolation system that issubstantially free from any noise interference that may have beenintroduced at the capacitive isolation barrier.

Preferred embodiments of active diode bridge circuit 640 of FIG. 2 aredetailed in FIG. 6A for single-ended digital communication and FIG. 6Bfor differential digital communication across the isolation barrier. Theactive diode bridge generates a DC power supply voltage V_(DD), whichmay be used to operate the clock recovery and receiver decoder circuits,in response to the digital data received across the capacitive isolationbarrier. An active diode bridge circuit is distinguished from a standardor passive diode bridge in that the gating elements are activetransistors rather than passive elements such as bipolar diodes.

Referring to the exemplary circuit illustrated in FIG. 6A, isolationcapacitor 209 is connected to node 625 and isolation capacitor 210 isconnected to node 626. The source of n-channel MOSFET 621 and the sourceof p-channel MOSFET 622 are connected to node 625. Also connected tonode 625 is the input of standard CMOS inverter 623. The output ofinverter 623 drives the gates of MOSFETS 621 and 622. The drain ofn-channel MOSFET 621 is connected to node 626, the receive circuitground node, while the drain of p-channel MOSFET 622 connects to node627, which provides V_(DD) voltage for the isolated circuitry. Alsoconnected to V_(DD) node 627 are load capacitor C_(L) 624 and the powersupply input of CMOS inverter 623. In a preferred embodiment, the powersupply inputs of clock recovery circuit 216 and decoder circuit 217shown in FIG. 2 are also connected to V_(DD) node 627.

Referring to the exemplary embodiment illustrated in FIG. 6A, theoperation of the active diode bridge circuit used in single-endeddigital communication will now be described. A digital logic signal iscoupled across capacitor 209 from the transmit section. When a digital“high” signal is received through capacitor 209, node 625 goes high. Thelogic “high” signal on node 625 forces the CMOS inverter 623 output nodeto go low, turning off device 621 and turning on device 622.Consequently, current flows through capacitor 209, device 622, and fromV_(DD) to receive circuit ground through capacitor C_(L) and throughclock recovery and decoder circuitry shown in FIG. 2. The circuit iscompleted by current flow returning across the isolation barrier throughcapacitor 210. The current demand by circuitry on V_(DD) throughcapacitors 209 and 210 must be limited so that the voltage on node 625relative to node 626 can still be recognized as a digital high logiclevel. When a digital “low” signal is received through capacitor 209,CMOS inverter 623 turns off device 622 and turns on device 621.Consequently, current flows across the isolation barrier throughcapacitor 210, through device 621, and returns across the isolationbarrier through capacitor 209. Therefore, although no average currentflows through capacitors 209 and 210, average current can be suppliedfrom V_(DD) to receive circuit ground to operate clock recovery circuit216 and decoder circuit 217. Load capacitor 624 operates to minimizesupply ripple on the DC supply voltage established on node V_(DD).

Referring to the embodiment shown in FIG. 6B, isolation capacitor 209connects to node 646 and isolation capacitor 210 connects to node 647.The source node of n-channel MOSFET 641 and the source node of p-channelMOSFET 642 connect to node 646. Also connected to node 646 are the gatesof n-channel MOSFET 643 and p-channel MOSFET 644. The source node ofn-channel MOSFET 643 and the source node of p-channel MOSFET 644 connectto node 647. Also connected to node 647 are the gates of n-channelMOSFET 641 and p-channel MOSFET 642. The drains of devices 641 and 643are connected to the ground node of the receiving circuit. The drains ofdevices 642 and 644 are connected to the node 220, which provides V_(DD)voltage for the isolated circuitry. Also connected to V_(DD) node 220are load capacitor C_(L) 645 and the power supply inputs of clockrecovery circuit 216 and decoder circuit 217 as shown in FIG. 2.

Referring to the exemplary embodiment illustrated in FIG. 6B, theoperation of the active diode bridge used in differential digitalcommunication will now be described. A differential digital signal isreceived through capacitors 209 and 210. When a digital ‘high’ signal isreceived through capacitor 209, a corresponding digital ‘low’ signal isreceived through capacitor 210, and node 646 goes high while node 647goes low. This condition turns on devices 642 and 643 while turning offdevices 641 and 644. Consequently, current flows through capacitor 209,device 642, from V_(DD) to ground through capacitor C_(L) and throughclock recovery circuitry 216 and decoder circuitry 217 shown in FIG. 2.The circuit is completed from receive circuit ground 650, through device643 and finally returning across the isolation barrier through capacitor210. The current demand on V_(DD) must be limited so that the voltage onnode 646 relative to node 650 can be recognized as a high logic levelsignal by the clock recovery and decoder circuitry.

When a digital ‘low’ signal is received through capacitor 209, a digital‘high’ signal is received through capacitor 210, and node 646 goes lowwhile node 647 goes high. This condition turns on devices 641 and 644while turning off devices 642 and 643. Consequently current flowsthrough capacitor 210 and device 644 to V_(DD) node 220, and from thereto ground through capacitor 645 and through clock recovery and decodercircuitry shown in FIG. 2. The circuit is completed from ground 650,through device 641 and finally returning across the isolation barrierthrough capacitor 209. Therefore, in either logic state, andindependently of the current flow direction through capacitors 209 and210, current flows in the same direction from V_(DD) to ground.Therefore, an average or DC supply voltage is established on nodeV_(DD), and adequate current can be supplied to operate clock recoverycircuit 216 and decoder circuit 217. Load capacitor 645 operates tominimize power supply ripple, providing a filtering operation on V_(DD).An added benefit of the ability to power sections of the isolatedcircuitry from the digital signal transmitted across the capacitiveisolation barrier from the powered circuitry is that it allows isolatedpower-up and power-down control of isolated circuitry sections on anas-needed basis.

Parasitic bipolar transistors may result from typical CMOS processes. Ifthey are not controlled, these bipolar transistors can discharge thepower supply 627 shown in FIG. 6A during the initial power up time. Ifthe discharge current from the parasitic bipolar transistors is largerthan the current delivered to the power supply 627 through transistor622, then the circuit may not power up to the desired full voltagelevel. The beta of a lateral bipolar transistor in any CMOS process is afunction of layout. With appropriate layout (i.e., large base region),the beta can be kept small enough to minimize undesired dischargecurrents. Further care needs to be taken in the design of any circuitthat is connected to power supply 627. The circuits connected to powersupply 627 cannot draw more current from the power supply than isavailable from the active diode bridge, even before the supply hasramped to the full value. Circuit design techniques to address theseissues are common and well known in the art.

In the illustrative embodiment shown in FIG. 2, delta-sigma digital toanalog converter (DAC) 208 receives input data from decoder 217 andsynchronous clock input from clock recovery circuit 216. Analog outputsignal 218 is generated by DAC 208 in response to the digital data thatis communicated across the capacitive isolation barrier. The outputsignal 218 is highly immune to amplitude and phase noise that may beintroduced in the barrier circuitry because the signal that iscommunicated across the isolation capacitors is a synchronous digitalsignal, and because the received data is resynchronized to therecovered, jitter-filtered clock signal. The DAC is also timed by thatclock signal. Delta-sigma DAC technology is well known in the art, andselecting a suitable DAC circuit will be a matter of routine designchoice directed to the intended application of the barrier circuit. See,for example, P. Naus et al., A CMOS Stereo 16-Bit D/A Converter forDigital Audio, IEEE Journal of Solid State Circuits, June 1987, pp.390-395, which is incorporated herein by reference.

FIG. 7 illustrates a preferred bidirectional embodiment of the presentinvention. It will be recognized that other unidirectional andbidirectional isolation barriers may be designed by persons skilled inthe art using the principles described herein, and that such barrierswill fall within the scope of this invention. In the illustrated anddescribed embodiment, the capacitive isolation system comprises a“transmit” system to the left of center, a “receive” system to the rightof center, and a capacitive isolation barrier in the center of thefigure comprising two high voltage capacitors 705 and 706. Note that theterms “transmit” and “receive” are used to identify the powered andisolated sides of the barrier, respectively, and that in this embodimentdata may be conveyed across the barrier in both directions. Many of thecomponents in this bidirectional embodiment are identical or similar tothose in the unidirectional embodiment described above with reference toFIG. 2.

The transmit system includes delta-sigma analog-to-digital converter 701operable on the analog input 720 of the transmit circuit andsynchronized to clock signal 722 from oscillator 704. The analog input720 of the transmit system is an analog signal containing information tobe transmitted across the isolation barrier, which may be for example ananalog voice signal to be coupled to a telephone system. Digital output724 of the delta-sigma ADC may be time-division multiplexed with digitalcontrol input 726 by the encoder circuit 702. Digital control input 726is a digital signal containing additional information to be transmittedacross isolation barrier 705, 706. Digital control input 726 may includecontrol information for analog circuitry on the receiving side of theisolation barrier. Encoder circuit 702 also formats the resulting datastream into a coding scheme that allows for robust clock recovery on thereceiving side of the isolation barrier, as is described above.

Encoder circuit 702 also receives a clock signal 722 from oscillator704. Driver circuit 703 of the transmit system drives the encoded signalto isolation capacitors 705 and 706 in response to the output of encodercircuit 702.

The isolation barrier comprises two high voltage capacitors 705, 706. Inone embodiment, capacitor 705 is driven bidirectionally by drivers 703,713 while capacitor 706 provides a return path across the isolationbarrier. In another embodiment of the present invention, capacitors 705and 706 are differentially driven by digital driver circuits 703, 713.

A preferred embodiment of the receive system, shown to the right ofisolation capacitors 705, 706 in FIG. 7 includes clock recovery circuit707, whose inputs are connected to isolation capacitors 705, 706. Theclock recovery circuit recovers a clock signal from the digital datadriven across the isolation barrier and provides synchronized clocksignal 730 to the various circuits in the receive system. The recoveredclock operates as the time base for decoder 708 and delta-sigmadigital-to-analog converter 709. Decoder section 708 separates the timedivision multiplexed data and control information, providing digitalcontrol output 732 to other circuitry, and providing synchronous datasignal 734 as an input to delta-sigma DAC 709. The delta-sigma DAC 709,with digital input 734 supplied by decoder 708, and clock signal 730supplied by clock recovery section 707, operates synchronously with thetransmit system delta-sigma ADC 701 and provides analog output 736 onthe receiving side of the isolation barrier. Active diode bridge 710 isconnected to isolation capacitors 705 and 706 and supplies a DC powersupply voltage to clock recovery circuit 707 and decoder circuit 708 bydrawing current from the digital signal transmitted across the isolationbarrier, as is described in detail above. Driver 713 must remaintri-stated until decoder 708 has detected a valid frame, indicatingsuccessful power-up of the receive circuit sections.

The embodiment shown in FIG. 7 also enables communication from thereceive system to the transmit system, or from right to left across theisolation capacitors as illustrated. The receive system encoder circuit712 and driver circuit 713 cooperate to communicate information backfrom the receive system to the decoder circuit 714 in the transmitsystem. Receive system encoder section 712 receives a clock input 730from clock recovery section 707, and is thereby synchronized to thetransmit system oscillator 704 and encoder 702. This synchronizationallows transmission in each direction to occur in distinct time slots.In time slots where transmit driver 703 is operable to transmitinformation from the transmit system to the receive system, receivedriver 713 is tri-stated or disabled. Alternatively, in time slots wherereceive driver 713 is operable to transmit information back from thereceive system to the transmit system, transmit driver 703 is tri-statedor disabled. In this manner, bidirectional communication may beestablished across a single pair of high voltage isolation capacitors.

Digital control input 738 of the receive system is a digital signalcontaining information to be communicated across the isolation barrier,including control information for analog circuitry on the transmitsystem side of the barrier. The receive system also includes delta-sigmaADC 711 operable on analog input signal 740 so that the informationcontained in analog signal 740 on the receive system side of theisolation barrier can be conveyed across the barrier in digital form andthen accurately reproduced on the transmit system side of the barrier.The receive system delta-sigma ADC 711 receives its clock input fromclock recovery circuit 707, and is thereby synchronized with transmitsystem oscillator 704. Digital output signal 742 generated by receivesystem ADC 711 may be time-division multiplexed with receive systemdigital control input 738 in encoder section 712.

In the transmit system, decoder circuit 714 is connected to isolationcapacitors 705, 706 to receive signals therefrom, identify signalsrepresenting information coming from the receive system. Decoder 714then extracts the digital control information from the data streamreceived from the receive circuit, and passes data signal 744 generatedby delta-sigma ADC 711 to transmit system delta-sigma DAC 715. Decoder714 also latches and retimes the data received across the barrier tosynchronize it with clock signal 722, which is generated by oscillator704, thereby eliminating the effects of phase noise interference andother sources of jitter in the synchronous digital signal. Circuits thatare suitable for performing these decoder functions are well known inthe art.

Transmit system delta-sigma DAC 715 receives its clock input fromoscillator 704 and is thereby synchronized to receive system ADC 711.Transmit system DAC 715 provides a reconstructed analog data outputsignal 746, thereby completing the communication of analog informationback from the receive system to the transmit system.

In summary, FIG. 7 describes a bidirectional communication system forconveying.analog and digital information across a capacitive isolationbarrier. The barrier itself is inexpensive, since only two high voltageisolation capacitors are required for synchronous, bidirectionalcommunication. The barrier is a reliable communication channel becausethe digital signals communicated across the barrier are insensitive toamplitude and phase noise interference that may be introduced at theisolation barrier.

A more detailed description of a clock recovery circuit suitable for usein this invention with the coding scheme of FIG. 4 will now be provided,with reference to FIG. 8. Clock recovery PLL 805 has data input 530,data output 546 and recovered clock signal output 544. Phase detector810 has inputs DATA 530 and feedback clock signal CK2 545. The outputsof phase detector 810 are SPEED-UP1 and SLOW-DOWN1 signals, both ofwhich are connected to inputs of phase detector charge pump 816.Frequency detector 818 has inputs DATA 530 and output clock signal CK4544. The outputs of frequency detector 818 are signals designatedSPEED-UP2 and SLOW-DOWN2, which are connected to the inputs of frequencydetector charge pump 824. The outputs of phase detector charge pump 816and frequency detector charge pump 824 are connected together and arealso connected to the input of voltage controlled oscillator (“VCO”) 535and one terminal of resistor 533. The other terminal of resistor 533 isconnected to one terminal of capacitor 534. The other terminal ofcapacitor 534 is connected to ground. The output of VCO 535 is the CK2signal 545. The clock input of flip-flop 826 is connected to CK2 545.The Q-bar output of flip-flop 826 is connected to the D input offlip-flop 826. The Q and Q-bar outputs of flip-flop 826 are connected tothe inputs of multiplexer (mux) 828. The control input 830 of mux 828 iscalled MUX CONTROL and comes from the framing logic, which is describedelsewhere in this specification. The output of mux 828 is the CK4 signal544. The D input of flip-flop 542 is connected to data input 530. Theclock input of flip-flop 542 is connected to the CK4 signal 544. The Qoutput of flip-flop 542 is the resynchronized DATAOUT signal 546, whichis sent to the frame detect logic.

Frequency detector 818 is dominant over phase detector 810 when thefrequency of the DATA and CK4 signals are different. Once the frequencyof the DATA and CK4 signals are substantially similar, the SPEED-UP2 andSLOW-DOWN2 signals become inactive and phase detector 810 becomesdominant. Separate charge pumps for the phase detector and frequencydetector allow for independent control of the gain of the phase detectorand frequency detector circuits. Alternatively, if independent gains arenot required, then the SPEED-UP1 and SPEED-UP2 signals could belogically ORed together to drive one charge pump. And likewise theSLOW-DOWN1 and SLOW-DOWN2 signals could be logically ORed together todrive the other input to the charge pump.

The output of VCO 535 is the CK2 signal, which is divided by two infrequency by flip-flop 826. Since CK2 is divided by two to generate thebit rate clock signal CK4, there can be two phases of CK4 with respectto the start of a bit period. The phase of CK4 that will yield correctoperation of the frequency detector is the one where the rising edge ofCK4 aligns with the start of a bit period. The frame-detect logic isneeded to detect the start of a bit interval and is used to select theappropriate phase of CK4 using mux 828.

It will be appreciated that a clock recovery circuit according to thisinvention, such as that illustrated in FIG. 8 or FIG. 15, may bebeneficially used to recover and stabilize a clock signal on theisolated side of the barrier where the clock signal is conveyed viaisolation elements that are separate from the isolation elements thatare used to transfer the data signal.

A preferred embodiment of a decoder circuit 708 is shown in FIG. 11.Shift register 840 has an input connected to the DATAOUT signal 546 fromclock recovery circuit 805 and is clocked by recovered clock signal CK4.Multi-bit output 842 of shift register 840 is connected to frame-detectlogic 844 and to demux logic 846. Frame detect logic 844 has one outputconnected to mux control logic 848 and one output connected to demuxlogic 846. Demux logic 846 is clocked by CK4. Counter. 850 is alsoclocked by CK4. The output of counter 850 is connected to mux controllogic 848. The output of mux control logic 848 is the MUX-CONTROL signal830 sent to the clock recovery PLL 805 to select the proper phase forthe CK4 signal. The outputs of demux logic 846 are the DEMUXED DATAsignal and the CONTROL signal.

Shift register 840 stores a predetermined number of bits of the serialDATAOUT signal 546. Frame-detect logic 844 operates on this data anddetects when a frame signal is received. Many possible framing signalformats can be used. A format that may be used in a presently preferredembodiment is shown in FIG. 12. Data 860 is alternated with framingsignals 862 and control signals. In the framing format shown in thisfigure, one control signal (off hook) 864 is sent for every eight databits. The remaining seven bits in the frame of sixteen are used forframe synchronization. The illustrated framing signal is six onesfollowed by a zero in the control signal field. The data signal may beguaranteed to not have more than five ones in a row so that it will notbe mistaken for a framing signal. Many other framing formats arepossible to allow for different data signal properties and to permit theuse of additional control bits.

Once the frame detect logic 844 detects six one's followed by a zero inthe control signal field, mux control logic 848 is set to maintain thephase of the CK4 signal. If after a predetermined number of CK4 clockcycles a framing signal is not detected, then counter 850 will cause muxcontrol logic 848 to change the phase of CK4 using mux 828 (FIG. 8).Counter 850 will then be reset, and frame detect logic 844 will againattempt to detect the selected framing signal so as to achievesynchronization. Only the correct phase of CK4 will achieve framesynchronization. Once frame synchronization is achieved, demux logic 846can correctly decode control and data signals.

The specific structure and operation of frame detect logic 844, demuxlogic 846, and mux control logic 848 is dependent upon the selectedframing format, the selected multiplexing scheme, and other designchoices. The detailed design of this circuitry is within the ordinaryskill in the art and is omitted from this description of a preferredembodiment.

Exemplary embodiments of phase and frequency detectors 810, 818 areshown in FIGS. 9 and 10. Referring to FIG. 9, phase detector 810 hasinput signals CK2 and DATA and output signals SPEED-UP1 and SLOW-DOWN1.A two input NAND gate 860 has inputs DATA and CK2 and its output isconnected to one input of NAND gate 862. A two input NOR gate 864 alsohas inputs DATA and CK2 and its output is connected to the input ofinverter 866. A two input NAND gate 868 has one input connected to theoutput of the inverter 866 and one input connected to the output of NANDgate 862. NAND gate 862 has one input that is connected to the output ofNAND gate 860 and the other input connected to the output of NAND gate868. A three input AND gate 870 has one input connected to the output ofinverter 872, another input connected to the DATA signal and anotherinput connected to the output of NAND gate 862. The output of AND gate870 is the SLOW-DOWN1 signal. The input of inverter 872 is connected tothe CK2 signal. A three input AND gate 874 has one input connected tothe output of NAND gate 862, another input is connected to the CK2signal and another input is connected to the output of inverter 876. Theoutput of AND gate 874 is the SPEED-UP1 signal. The input of inverter876 is connected to receive the DATA signal.

In the illustrated embodiment, phase detector 810 compares the phase onthe falling edges of DATA and CK2 after both signals are high at thesame time. NAND gates 862 and 868 form a set-reset type latch. The latchgets “set” such that the output of NAND gate 862 is high when both theDATA and CK2 signals are high. The latch gets “reset” such that theoutput of NAND gate 862 is low when both DATA and CK2 are low. When thelatch is “set” (i.e., both DATA and CK2 are high), AND gates 870 and 874are enabled. Once the AND gates 870 and 874 are enabled they can comparethe falling edges of CK2 and DATA to determine which signal goes lowfirst. If DATA goes low first, then the SPEED-UP1 signal will go highuntil CK2 also goes low, indicating that oscillator 535 needs tooscillate faster in order to achieve phase alignment with the DATAsignal. If the CK2 signal goes low first then the SLOW-DOWN1 signal willgo high until DATA also goes low, indicating that oscillator 535 shouldoscillate slower in order to achieve phase alignment with the DATAsignal. The SPEED-UP1 and SLOW-DOWN1 signals are connected to phasedetector charge-pump 816.

A preferred embodiment of frequency detector 818 is shown in FIG. 10.The inputs to frequency detector 818 are the DATA and CK4 signals andthe outputs are the SPEED-UP2 and SLOW-DOWN2 signals. Delay cell 880 hasits input connected to CK4 and output connected to one input of NOR gate882. The delay cell 880 consists of an even number of capacitivelyloaded inverter stages or other delay generating circuitry and is wellknown in the art. The output of inverter 884 is connected to the otherinput of NOR gate 882 and the input of inverter 884 is connected to CK4.The output 886 of NOR gate 882 is reset pulse that occurs on the risingedge of CK4, and is connected to the reset input of D flip-flops 888,890, and 892. The input of inverter 895 is connected to DATA. The outputof inverter 895 is connected to the clock input of D flip-flops 888,890, and 892. The D input of flip-flop 888 is connected to V_(DD). TheD-input of flip-flop 890 is connected to the Q-output of flip-flop 888.The D-input of flip-flop 892 is connected to the Q-output of flip-flop890. D flip-flops 894 and 896 have their clock inputs connected to CK4.The D input of flip-flop 894 is connected to the Q output: of flip-flop888. The D-input of flip-flop 896 is connected to the Q-output offlip-flop 890. The input of inverter 898 is connected to the Q-output offlip-flop 894, and the output of inverter 898 is the SLOW-DOWN2 signal.OR gate 900 provides the SPEED-UP2 signal. One input of OR gate 900 isconnected to the Q-output of flip-flop 896, and the other input isconnected to the Q-output of flip-flop 892. The SPEED-UP2 and SLOW-DOWN2signals are connected to the frequency-detector charge pump 824. .

The illustrated embodiment of frequency detector 818 counts the numberof DATA pulses within one CK4 cycle. The frequency of CK4 should equalto the bit rate of the DATA pattern. Suitable encoding used for the DATAsignal will ensure that there will be only one CK4 rising edge for eachdata pulse falling edge, if the frequency of CK4 is equal to the datarate. If the CK4 frequency is equal to the data rate then the Q-outputof flip-flop 888 will be high prior to each rising edge of CK4 and theQ-outputs of flip-flops 890 and 892 will be low prior to each risingedge of CK4. If the Q-output of flip-flop 888 is low prior to the risingedge of CK4 then the SLOW-DOWN2 signal will go high for the duration ofthe next CK4 cycle, signaling that oscillator 535 should slow down. Ifthe Q-output of flip-flop 890 is high prior to the rising edge of CK4,then the SPEED-UP2 signal will go high for the duration of the next CK4cycle signaling that the oscillator should speed up.

Another exemplary data coding scheme that may be used in an isolationsystem constructed in accordance with this invention is shown in FIG.14. In this scheme, each bit period 570 is split into four fields. Thefirst field 572 is referred to as the clock field and is always highindependent of the data being transferred. The second field 574, whichmay occupy the second quarter of the bit period 570, contains theforward-going (from transmit side to receive side) data bit. This databit can be either the delta-sigma data bit or a control bit or anydesired type of encoding bit, in accordance with the requirements of theapplication in which the invention is used. The third field 576, whichmay occupy the third quarter of the bit period, is always low to ensureenough signal transitions to provide for power transmission in theforward path along with the first two fields, at least one of which ishigh in each bit period. The forward (transmit side) driver circuit istri-stated during the fourth field 578, thus allowing for datatransmission in the opposite direction across the isolation capacitor.Of course, this particular coding scheme is provided as an example, andmany other coding schemes may be devised that will be operable in thevarious embodiments of the present invention.

It is desirable to use the logic “1” that is present at the beginning ofeach bit period for clock recovery, since it is always present atperiodic intervals. However, if the reverse data bit from the previousbit period is a one, the rising edge at the beginning of the next bitperiod will not be readily seen by a logic gate and therefore will notbe useful for clock recovery. To mitigate this effect and to allowreliable clock recovery, every fourth bit in the reverse field may beguaranteed to be zero by the encoding algorithms that are employed. Thetotal frame length can be increased if more control bits need to be sentacross the barrier in the reverse direction. Every fourth clock edge(the one associated with a zero in the previous reverse bit field ) maythen be used for clock recovery.

A block diagram of an exemplary PLL circuit that can perform clockrecovery in accordance with the coding scheme of FIG. 14 is shown inFIG. 15. The forward data (conveyed from the transmit side to thereceive side) is connected to divide-by-four counter 800. The output ofcounter 800 is connected to phase-frequency detector 801. The output ofphase-frequency detector 801 is connected to charge pump 802. The outputof charge pump 802 is connected to the input of loop filter 803. Theoutput of loop filter 803 is connected to the input of voltagecontrolled oscillator (VCO) 804. The output of VCO 804 is the bit clockused for synchronizing the received data signal and for providing aclock signal to the receive side circuitry. The output of VCO 804 isalso connected to the input of divide-by-four counter 805. The output ofcounter 805 is connected to the other input of phase-frequency detector801. The phase-frequency detector 801 and the other circuits in theillustrated clock recovery circuit of FIG. 15 are well known in the art,and the specific circuitry selected for a particular application wouldbe a matter of routine design choice.

FIG. 16 is a general block diagram of digital DAA circuitry 110including phone line side circuitry 118, an isolation barrier 120, andpowered side circuitry 116 according to the present invention. Theisolation barrier 120 may include one or more capacitors and allow forthe transmission of digital information between the isolation interface1614 in the phone line side circuitry and the isolation interface 1610in the powered side circuitry. The phone line side circuitry 118 may beconnected to phone lines of a telephone network system, and the poweredside circuitry 116 may be connected to external controllers, such asdigital signal processors (DSP), that may be part of a communicationdevice, such as a phone or modem.

The powered side circuitry 116, which may be implemented as anintegrated circuit (IC), may communicate with the external controllerthrough a digital interface 1606 and a control interface 1608. Forexample, the digital interface 1606 may have a number of external pinsproviding a serial port interface to the external controller, such as amaster clock input pin (MCLK), a serial port bit clock output (SCLK), aserial port data IN pin (SDI), a serial port data OUT pin (SDO), a framesync output pin (FSYNC_bar), and a secondary transfer request input pin(FC). Similarly, the control interface 1608 may have a number ofexternal pins providing control and status information to and from theexternal controller, such as a ring detect status pin (RGDT_bar), anoff-hook status pin (OFHK_bar), a reset pin (RESET_bar), and multiplemode select pins (MODE). (It is noted that the suffix “_bar” is used todenote a signal that is typically asserted when at a low logic level.)In addition, the digital interface 1606 and the control interface 1608are connected to the isolation interface 1610 so that control, status,signal and other desired information may be transmitted to and receivedfrom the phone line side circuitry 118 across the isolation barrier 120.

The phone line side circuitry 118, which may be implemented as anintegrated circuit (IC), may communicate with the phone lines throughhybrid circuitry 1616, may receive DC power and provide an internalpower supply voltage through DC termination circuitry 1618, anddetermine ring-detect and off-hook status information throughoff-hook/ring-detect block 1620. In addition, the hybrid circuitry 1616,the off-hook/ring-detect block 1620, and the DC termination circuitry1618 are connected to the isolation interface 1614 so that control,status, signal and other desired information may be transmitted to andreceived from the powered side circuitry 116 across the isolationbarrier 120.

In the embodiment depicted, the hybrid circuitry 1616 has an output pin(TX) and an input pin (RX) that may connect to external telephoneinterface circuitry such as hook-switch circuitry and a diode bridge.The hybrid circuitry 1616 may function to split the differential signalexisting on the phone, which typically includes both transmit andreceive analog information, into an internal transmit signal (TX_(INT))and receive signal (RX_(INT)). It is noted that the TX output pin islabeled to indicate that it is used to transmit analog information tothe phone lines, and that the RX pin is labeled to indicate that it isused to receive analog information from the phone lines. These externalpin signals are different than the internal analog transmit signal(TX_(INT)) and analog receive signal (RX_(INT)).

The DC termination circuitry 1618 may have a number of external pinsthat also connect to external telephone interface circuitry such ashook-switch circuitry and a diode bridge. For example, the DCtermination circuitry 1618 may have a DC termination pin (DCT), avoltage regulator pin (VREG), an external resistor pin (REXT), and aisolated ground pin (IGND). The DC termination circuitry 1618 terminatesthe DC voltage on the phone line and provides an internal power supplyfor the phone line side circuitry 118. The DC termination pin (DCT)receives the phone line DC current. The voltage regulator pin (VREG)allows external regulator circuitry, such as a capacitor, to beconnected to the DC termination circuitry 1618. An external powerdissipating resistor may be connected to the external resistor pin(REXT). And the isolated ground pin (IGND) may be connected to thesystem ground for the powered side circuitry 116 through a capacitorwithin the isolation barrier 120 and may also be connected to the phoneline through a ground connection within external diode bridge circuitry.

The off-hook/ring-detect block 1620 may have external input pinsallowing status information to be provided concerning phone line statusinformation (RNG1, RNG2), such as ring and caller identificationsignals. For example, the first ring detect pin (RNG1) may connect tothe tip (T) lead of the phone line through a capacitor (2200 pF), andthe second ring detect pin (RNG2) may connect to the ring (R) lead ofthe phone line through a capacitor (2200 pF). In addition,off-hook/ring-detect block 1620 may have external output pins (QB, QE)that control external off-hook circuitry to enter, for example, anoff-hook state or a limited power mode to get caller identificationinformation. In addition, the output pins (QB, QE) may be connected tothe base and emitter, respectively, of a bipolar transistor withinexternal hook-switch circuitry.

FIG. 17 is a general block diagram of internal transmit (TX) and receive(RX) signal paths within digital DAA circuitry 110 according to thepresent invention. In the embodiment depicted, information maycommunicated in either direction across the isolation barrier 120. It isnoted that FIG. 17 does not depict all of the functional blocks withinpowered side circuitry 116 and phone line side circuitry 118. It is alsonoted that the blocks depicted may be implemented as numerous additionalblocks carrying out similar functions.

In the embodiment of FIG. 17, communications from the phone line sidecircuitry 118 to the powered circuitry 116 are considered receivesignals. Within phone line side circuitry 118, a delta-sigmaanalog-to-digital converter (ADC) 1710 receives an internal analogreceive signal (RX_(INT)), which may be provided for example by hybridcircuitry1616. The output of delta-sigma ADC 1710 is oversampled digitaldata stream in a pulse density modulation format. The decoder/encodercircuitry 1708 processes and formats this digital information as desiredbefore sending it across the isolation barrier 120 as encoded digitalinformation. For example, decoder/encoder 1708 may multiplex controldata with the digital stream before it is sent across the isolationbarrier 120. This control data may be a any desired information, such asring detect signals, off-hook detect signals, or other phone line statusinformation. Within powered side circuitry 116, the decoder/encoder 1706decodes this encoded digital information received across the isolationbarrier 120. The digital filter 1702 processes this decoded digitalstream and converts it into internal digital receive data (RX_(D)) thatmay be provided through the digital interface 1606 to an externalcontroller.

Communications from the powered side circuitry 116 to the phone lineside circuitry 118 are considered transmit signals. Within powered sidecircuitry 116, a delta-sigma modulator 1704 receives an internal digitaltransmit signal (TX_(D)), which may be provided for example from anexternal controller through digital interface 1606. The output ofdelta-sigma modulator 1704 is an oversampled digital data stream in apulse density modulation format. The decoder/encoder circuitry 1706processes and formats this digital information as desired before sendingit across the isolation barrier 120 as encoded digital information. Forexample, decoder/encoder 1706 may multiplex control data with thedigital stream. This control data may be a any desired information, suchas ring detect signals, off-hook detect signals, or other phone linestatus information. In addition, decoder/encoder 1706 may add framinginformation for synchronization purposes to the digital stream before itis sent across the isolation barrier 120. Still further, decoder/encoder1706 may format the digital data stream so that a clock signal may berecovered within the phone line side circuitry 118, for example, as isdiscussed with respect to FIG. 14 above. Within phone line sidecircuitry 118, the decoder/encoder 1708 may recover a clock signal andmay decode the encoded digital information received across the isolationbarrier 120 to obtain framing, control or status information. Thedigital-to-analog converter (DAC) 1712 converts the decoded digitalstream and converts it into internal analog transmit data (TX_(INT))that may be provided as an analog signal through the hybrid circuitry1616 and ultimately to the phone lines.

FIG. 18 is a general circuit diagram of digital DAA circuitry 110implemented with a two integrated circuits (ICs) and a capacitiveisolation barrier 120 according to the present invention. In particular,powered side circuitry 116 may include a powered side integrated circuit(IC) 1802A, and phone line side circuitry 118 may include a phone lineside IC 1802B. External circuitry, such as hook-switch circuitry 1804and diode bridge circuitry 1806, is also shown connected to externalpins of the phone line side IC 1802B. In the embodiment depicted,external pins 1810 of the powered side IC 1802A are connected to anexternal digital signal processor (DSP) and the external pins 1808 areconnected to a external application specific IC (ASIC) or controller.The isolation barrier 120 may include a first capacitor (C1) connectingan external signal (C1A) pin on the powered side IC 1802A to an externalsignal (C1B) pin on the phone line side IC 1802B. In addition, theisolation barrier 120 may have a second capacitor (C2) connecting theisolated ground (IGND) pin on the phone line side IC 1802B to the systemground (GND) pin on the powered side IC 1802A. In addition, the isolatedground (IGND) pin may be connected to node 1812 within diode circuitry1806 and thereby be connected to the phone line.

FIGS. 19-20 illustrate an embodiment of the present invention for use ina Digital Subscriber Line (DSL) environment. DSL is a telephone looptechnology that uses existing telephone lines to provide a dedicated,high-speed data connection at speeds approaching 1.5 Mbps and beyond.Various types of DSL include Asymmetric Digital Subscriber Line (ADSL),High-bit-rate Digital Subscriber Line (HDSL), ISDN Digital SubscriberLine (IDSL), Rate Adaptive Digital Subscriber Line (RADSL), Single-LineDigital Subscriber Line (SDSL), Universal Digital Subscriber Line(UDSL), Very High Digital Subscriber Line (VDSL), etc. For the purposesof this description, the present invention will be described in an ADSLenvironment, although the invention may be used in other types ofenvironments.

FIG. 19 as a block diagram illustrating an application of the presentinvention in an ADSL environment. FIG. 19 shows a system 1910 connectedto external DC or AC power source 1912 and to public phone system 1914.The system 1910 includes powered circuitry 1916 which is powered byexternal power source 1912. Telephone system 1910 also includes voicecircuitry 1918, ADSL circuitry 1919, and plain old telephone system(POTS) splitter 1926.

Since signals received from public phone system 1914 contain both lowfrequency analog voice signals and high frequency digital ADSL signalsand the signals must generally be separated. The POTS splitter 1926separates the received signals into separate DSL data and voicechannels. The voice channel is sent to voice circuitry 1918 and the datachannel the sent to ADSL circuitry 1919. A typical POTS splitter iscomprised of a low pass filter for filtering out the high frequency datasignal and a high pass filter for filtering out the low frequency voicesignal. Other designs, for example splitterless designs, may also beused within the spirit and scope of the present invention. Similarly,the voice and data signals can be separated prior to being introduced tothe system 1910.

As mentioned above, in order to protect public phone system 1914, it isnecessary to isolate powered circuitry 1916 from the circuitry connectedto public phone system 1914, to prevent dangerous or destructive voltageor current levels from entering public phone system 1914. The requiredisolation is provided by isolation barrier 1920. The primaryrequirements placed on isolation barrier 1920 are that it effectivelyprevents harmful levels of electrical power from passing across it,while accurately passing the desired signal from the powered side 1922to the isolated side 1924, or in the reverse direction if desired.

FIG. 20 illustrates one embodiment of the present invention. Asmentioned above, the circuitry shown on the left side of the isolationbarrier will be referred to as the “powered” circuitry, and thecircuitry on the right side of the isolation barrier will be referred toas the “isolated” or “phone line side” circuitry. As shown in FIG. 20,powered circuitry 2016 includes ADSL transceiver unit (ATU) 2030 andvoice circuitry 2032. The powered circuitry 2016 may be coupled througha communication interface 2040 to a computer network, a computer, amodem, a telephone and other electronic circuitry. Isolated circuitry2028 includes POTS splitter 2026, voice circuitry 2018, and ADSLcircuitry 2019. Isolation barrier 2020 is comprised of capacitors C1,C2, and transformer T1. The circuitry designated as voice circuitry 2018and voice circuitry 2032 is similar to the telephone circuitry describedabove and is not limited to use with only “voice” data. For example, thevoice circuitry may be used with voice communications, caller ID data,modem communications, fax communications, or other types ofcommunications that use phone lines.

Since ADSL communication takes place on the same twisted pair used forvoiceband telephone communications, the ADSL and voice circuitry mustcoexist together. Further, the ADSL circuitry may be required to operatewhen the voice circuitry is in the “on-hook” state, thus limiting theamount of power which may be drawn from the phone lines to power theADSL circuitry. As a result, a relatively large amount of power mayneeded on the line side to accommodate ADSL communications and thispower may not be able to be supplied entirely from the phone line orthrough the capacitive elements of the isolation barrier 2020. As shownin FIG. 20, the isolation barrier may thus include transformer T1 toprovide the power necessary for ADSL circuitry 2019 to perform ADSLfunctions.

In typical ADSL systems, the signal conditioning and data conversionrequired for ADSL transmission may be performed on the powered side andthe ADSL signal is transmitted through a “signal” transformer onto thetwisted pair. In the embodiment illustrated in FIG. 20, transformer T1may be a pulse transformer. The pulse transformer may be used totransmit power and digital information from ATU 2030 to ADSL circuitry2019 which then performs the necessary signal conditioning and dataconversion, or alternatively, only power may transmitted across thetransformer and the digital ADSL information may be transmitted acrossthe capacitive elements C1 and C2. Alternatively, additional capacitorsmay be provided for communication of ADSL information. In circumstanceswhere only power is transmitted through the transformer T1, thetransformer quality (and expense) may be less than when using thetransformer also transmit data.

The capacitors C1 and C2 in isolation barrier 2020 function in a similarmanner to the capacitive barriers described above. As is describedabove, the capacitors C1 and C2 provide a means of communication acrossthe isolation barrier for transmitting and receiving digital signalsincluding digital data signals multiplexed with clock, digital control,signaling and framing information. FIG. 20 also shows connectionsbetween ATU 2030 and voice circuitry 2032 as well as between ADSLcircuitry 2019 and voice circuitry 2018. These connections are used toexchange any desired information, including data, timing or clocksignals, control information, etc.

As a result of using a pulse transformer to transmit power to ADSLcircuitry which then performs the signal conditioning and dataconversion, the transformer T1 may be comprised of a transformer that ischeaper than typical prior art ADSL transformers. In addition, the sametransformer can be used for different DSL standards that operate overdifferent frequency ranges. Also, the invention provides the ability tointegrate voice-band circuitry into the same integrated circuit as ADSLcircuitry.

The power transmitted across the transformer T1 may also be utilized toprovide a power supply for portions of the voice circuitry 2108. Thevoice circuitry 2108 may thus include circuitry that consumes more powerthan the embodiments discussed above with reference to FIGS. 1-18

Further modifications and alternative embodiments of this invention willbe apparent to those skilled in the art in view of this description.Accordingly, this description is to be construed as illustrative onlyand is for the purpose of teaching those skilled in the art the mannerof carrying out the invention. It is to be understood that the forms ofthe invention herein shown and described are to be taken as thepresently preferred embodiments. Various changes may be made in theshape, size and arrangement of parts. For example, equivalent elementsmay be substituted for those illustrated and described herein, andcertain features of the invention may be utilized independently of theuse of other features, all as would be apparent to one skilled in theart after having the benefit of this description of the invention.

We claim:
 1. A method of operating circuitry for terminating a phoneline connection, comprising: providing phone line side circuitryoperable to communicate with a capacitive isolation barrier and thephone line connection; utilizing digital information transmitted acrossthe capacitive isolation barrier to provide a phone line side clock; andutilizing digital information transmitted across the capacitiveisolation barrier to provide a power supply for at least a portion ofthe phone line side circuitry.
 2. The method of claim 1, wherein saidphone line side circuitry further comprises DSL circuitry that iscapable of being used for receiving DSL information transmitted acrosssaid capacitive isolation barrier.
 3. The method of claim 2, whereinsaid capacitive isolation barrier is comprised of a plurality ofcapacitors.
 4. The method of claim 2, wherein said capacitive isolationbarrier is comprised of at least one transformer and one or morecapacitors.
 5. The method of claim 4, wherein said transformer iscomprised of a pulse transformer.
 6. The method of claim 2, furthercomprising providing powered side circuitry, wherein said powered sidecircuitry further comprises powered side DSL circuitry that may be usedfor transmitting DSL information across said capacitive isolationbarrier.
 7. The method of claim 6, wherein said capacitive isolationbarrier is comprised of at least one transformer.
 8. The method of claim7, wherein said transformer powers said DSL circuitry.
 9. The method ofclaim 7, wherein said DSL information is transmitted across saidtransformer.
 10. Circuitry for terminating a phone line connection,comprising: powered side circuitry operable to communicate digitallywith phone line side circuitry, said digital communication comprising adigital data stream transmitted across a isolation barrier through afirst bi-directional connection; the isolation barrier including atleast one capacitor and phone line side circuitry operable tocommunicate digitally with powered side circuitry, said digitalcommunication comprising a digital data stream transmitted across saidisolation barrier through a second bi-directional connection.
 11. Thecircuitry of claim 10, wherein said powered side circuitry furthercomprises powered side DSL circuitry and said phone line side circuitryfurther comprises phone line side DSL circuitry.
 12. The circuitry ofclaim 11, wherein said isolation barrier comprises a plurality ofcapacitors.
 13. The circuitry of claim 12, wherein said isolationbarrier further comprises a transformer.
 14. The circuitry of claim 13,wherein said transformer is a pulse transformer.
 15. The circuitry ofclaim 13, wherein said transformer powers said phone line side DSLcircuitry.
 16. The circuitry of claim 13, wherein said powered side DSLcircuitry includes encode circuitry to generate an encoded digital DSLsignal for transmission across said isolation barrier and wherein saidphone line side DSL circuitry includes decode circuitry to generate adecoded digital DSL signal from said encoded digital DSL signal.
 17. Amethod for communicating with phone lines, comprising: converting adigital signal into a digital data stream; communicating said digitaldata stream across an isolation barrier from a bi-directional connectionon powered side circuitry to a bi-directional connection on phone lineside circuitry, said communication being bi-directional through at leastone capacitive element; and utilizing the digital data stream togenerate a power supply within the phone line side circuitry.
 18. Themethod of claim 17, wherein said powered side circuitry includes poweredside DSL circuitry and wherein said phone line side circuitry includesphone line side DSL circuitry.
 19. The method of claim 18, wherein saidisolation barrier comprises a plurality of capacitors.
 20. The method ofclaim 19, wherein said isolation barrier further comprises atransformer.
 21. The method of claim 20, wherein said phone line sideDSL circuitry is powered by said transformer.
 22. Circuitry forterminating a phone line connection, comprising: powered side circuitryoperable to communicate digitally with phone line side circuitry througha first node capable of communicating with a capacitive isolationbarrier; phone line side circuitry operable to communicate digitallywith the powered side circuitry through a second node capable ofcommunicating with the capacitive isolation barrier; a clock signalwithin the phone line side circuitry, the clock signal capable of beinggenerated from information transmitted across the capacitive isolationbarrier; at least one power supply within the phone line side circuitry,the power supply capable of being generated from information transmittedacross the capacitive isolation barrier; and at least one control signalwithin the phone line side circuitry, the control signal being capableof being transmitted across the capacitive isolation barrier.
 23. Thecircuitry of claim 22, wherein the powered side circuitry furthercomprises powered side DSL circuitry and the phone line side circuitryfurther comprises phone line side DSL circuitry.
 24. The circuitry ofclaim 23, wherein the capacitive isolation barrier further comprises atransformer.
 25. The circuitry of claim 24, wherein the transformer is apulse transformer.
 26. The circuitry of claim 24, wherein said phoneline side DSL circuitry is powered by said transformer.